# Chebyshev Bandpass Filter Using Resonator of Tunable Active Capacitor and Inductor.

1. IntroductionThe rapid development of complementary metal-of-semiconductor (CMOS) endues the integrated circuit with small size and low cost in both digital and analog applications. A wireless communication system mainly consists of three components: mixer, bandpass filter, and low noise amplifier. The bandpass filter blocks unwanted signals and selects desirable signal matched to different pass band mixers, that is, 1,920-1,980 MHz of WCDMA, 890-960 MHz of GSM, 1,575 MHz of GPS L1 BPF, and 2,400-2,483 MHz of 802.11b/g. Bandpass filter with high Q and good selectivity of center frequency and bandwidth is desirable in today's applications. The LC based passive bandpass filter has been used for several decades; however, when applied to the nanotechnology CMOS integrated circuit it confronts limitations. For example, the degraded performance of CMOS spiral inductor due to its significant resistive loss reduces BPF quality factor and restrains the gain and bandwidth [1, 2]. Inductors are bulky and expensive, significantly increasing the instability of integration and manufacturing cost. Tunable AC achieves in a wide capacitive range from 40 fF to 1 pF [1, 3] and tunable AI achieves in a wide inductive range from 1nH to 300 nH [4]. Therefore, using AC and AI to produce a small size and low cost BPF with tunable gain, tunable center frequency, and tunable bandwidth is a feasible and cost-effective solution. For this reason, eliminating resistive loss in AI will improve BPF quality factor.

Reducing resistive loss in the Chebyshev bandpass filter has been presented in improvement on pass band gain, bandwidth, and center frequency [1, 2, 5-8]. The tapped-inductor compensates the inductor resistive loss and adds an additional shunt feedback passive inductor to operate in the K-band [2]. The transformer-based passive inductor produces a frequency-dependent negative resistance for resistive loss compensation [8]. It operates at a center frequency of 2,368 MHz and a bandwidth of 60 MHz. But passive inductors make area much larger than active BPFs [5-7]. Inserting a gyrator-C based active inductor in a resonator demonstrates BPF applications at different frequency ranges [6, 7]. However, the BPF operating frequencies and bandwidths are not tunable. In [5] the BPF is designed to compensate frequency-dependent resistive loss for tunable center frequency. However, the complex structure consumes large area and power consumption. In [1] the BPF design incorporates an active capacitor with negative resistance to offset the resistive loss for large bandwidth. However, its tunability is limited due to mismatch between active capacitor's negative resistance and spiral inductor's positive resistance.

In this paper, a new BPF using tunable active capacitor and inductor is presented. Self-negative resistance of active capacitor is designed to compensate the positive resistance of active inductor, independent of signal frequency within its tunable range. Meanwhile, adjusting design parameters of the active component can control tunability of center frequency, gain, and bandwidth. The paper is organized as follows. Sections 2 and 3 discuss the principle design and operation of active capacitor and active inductor. Section 4 presents a compensation structural resonator using active capacitor and active inductor. This section also unfolds the performance of the BPF using the resonator. Finally, summary of this work and comparison with previous work are presented.

2. Tunable Active Capacitor in BPF

2.1. Large Signal Analysis of AC. The first active capacitor (AC) with negative resistance was demonstrated in [3]. The paper [1] adopted this AC structure and designed it in 0.18 [micro]m CMOS technology. In this section we extend the AC design principle to make it tunable and compensate resistive loss of the resonator in BPF. The active capacitor and its equivalent circuit are shown in Figure 1. The AC is designed by the cross-coupled pair of [M.sub.2] and [M.sub.3] and the resistive load [mathematical expression not reproducible] is controlled by [V.sub.D]. [V.sub.CC] is determined by [mathematical expression not reproducible] is controlled by VCC. In our design principle, we keep [V.sub.CC] > [V.sub.D] - [V.sub.t] to make [M.sub.2] in saturation and keep [V.sub.D] > [V.sub.CC] - [V.sub.t] to make [M.sub.3] in saturation. So, [V.sub.D] - [V.sub.t] < [V.sub.CC] < [V.sub.D] + [V.sub.t].

2.2. Small Signal Analysis of AC. The AC small signal model and its equivalent circuit are depicted in Figure 2. VG is almost the sum of [V.sub.CC] and [V.sub.D] as [V.sub.t] is small and [mathematical expression not reproducible], which expresses the relationship between [V.sub.CC] and [V.sub.in]. An easier way to analyze the small signal model is to set [V.sub.CC] = [[rho].sub.Vin] and [rho] is controlled by transistor parameters.

We continue to analyze the small signal model shown in Figure 2.

[mathematical expression not reproducible] (1)

Therefore,

[mathematical expression not reproducible]. (2)

So, the current source [mathematical expression not reproducible] can be flipped to opposite direction without changing the symbol. Also, [mathematical expression not reproducible]. The admittance from the input port is determined by [I.sub.in]/[V.sub.in].

[mathematical expression not reproducible]. (3)

[V.sub.CC] is the reference voltage shown in Figure 1. The branch currents [mathematical expression not reproducible] are

[mathematical expression not reproducible] (4)

At the reference point,

[mathematical expression not reproducible]. (5)

Therefore,

[mathematical expression not reproducible]. (6)

So,

[mathematical expression not reproducible]. (7)

From (7) expressing the negative resistance is controlled by the transconductance [mathematical expression not reproducible], transconductance [mathematical expression not reproducible], and transconductance [mathematical expression not reproducible] and the capacitance is determined by the gate-to-source capacitance of NMOS transistors. Adjusting these parameters will produce different negative resistance and capacitance values, which can be used to compensate the resistive loss of inductor.

2.3. AC Simulations. Figures 3 and 4 unfold the fact that tuning [V.sub.G] (from 1.6 V to 2.3 V) produces different capacitance values (from 128 fF to 175 fF) and negative resistance values (from -183 [OMEGA] to -338 [OMEGA]). For our applications, increasing VG will increase the capacitance value and decreases the negative resistance value. In the meantime, both capacitance and negative resistance values are stable and almost constant in a specific frequency range. For example, when [V.sub.G] varies from 1.6 V to 1.7 V, the capacitance increases from 128 fF to 148 fF and the negative resistance decreases from -338 [OMEGA] to -228 [OMEGA] (i.e., the corresponding negative conductance increases from -2.96 mS to -4.38 mS). The capacitance and negative resistance values are stable and constant in 3,859 MHz and 2,486 MHz frequency range, respectively.

3. Tunable Active Inductor in BPF

3.1. Gyrator-C Active Inductor (AI). Several active inductors have been proposed [4, 9-18]. Most are designed on the basis of the gyrator-C topology: (1) single-ended active inductors [9-13] and (2) differential active inductors [14-17]. A lossy single-ended gyrator-C active inductor is presented in Figure 5 to demonstrate how its structure performs an inductive function without use of any spiral inductors. The proposed active inductor is shown in Figure 6. Its structure is on the basis of the single-ended gyrator-C and its tunable active inductor [4]. Figure 7 shows its small signal model.

In Figure 5, [mathematical expression not reproducible] are the transconductance. [G.sub.1] and [G.sub.2] are the total conductance at nodes B and A, respectively. So, 1/[G.sub.1] is the sum of the output impedance of [mathematical expression not reproducible] and the input impedance of [mathematical expression not reproducible]. Similarly, 1/[G.sub.2] is the sum of the output impedance of [mathematical expression not reproducible] and the input impedance of [mathematical expression not reproducible]. [C.sub.1] and [C.sub.2] are the total capacitance at nodes B and A, respectively.

At node A,

[mathematical expression not reproducible]. (8)

I

At node B,

[mathematical expression not reproducible]. (9)

From node A, the input impedance equals

[mathematical expression not reproducible]. (10)

Compared with the simplified model of RLC circuit,

[mathematical expression not reproducible]. (11)

3.2. Signal Analysis of AI. Two pairs of current mirrors ([M.sub.0], [M.sub.1]) and ([M.sub.5], [M.sub.6]) are used in Figure 6. Both gate voltages of [M.sub.0] and [M.sub.5] are controllable by tuning [R.sub.1], [R.sub.2], [M.sub.1], and [R.sub.6], which controls current of [M.sub.0] and [M.sub.5]. [M.sub.2], [M.sub.3], and [M.sub.4] control small signal parameters like [mathematical expression not reproducible], and [mathematical expression not reproducible].

For the small signal model of the proposed active inductor, the input impedance equals

[mathematical expression not reproducible], (12)

[mathematical expression not reproducible]. (13)

[Y.sub.ins] is extracted from (13):

[mathematical expression not reproducible]. (14)

[mathematical expression not reproducible]. (15)

So,

[mathematical expression not reproducible]. (16)

Compared with the simplified model in Figure 5, it is shown that [mathematical expression not reproducible].

From the above analysis, [L.sub.equ] and [R.sub.s] are functions of [mathematical expression not reproducible]. Both are controllable by changing the large signal bias conditions as discussed in this section.

3.3. AI Simulations. Figures 8 and 9 show inductance and resistance values by tuning the DC bias voltage. The inductance varies from 1 to 300 nH and resistance varies from 43 to 344 Q. As shown in the plot, the highest inductive frequency range is achieved at 5,156 MHz with a peak inductance of 23 nH. By means of adjusting the bias conditions, different inductance and resistance values can be produced for different applications in a specific inductive frequency range. Figure 9 shows the tunable resistance. For example, when the active inductance value is adjusted from 1 nH to 300 nH, the resistance value changes from 344 [OMEGA] to 107 [OMEGA] and the frequency range is from 275 MHz to 770 MHz.

4. Chebyshev BPF Using Active Capacitor and Inductor

4.1. Design. The 2nd-order active BPF is designed based on the classic Chebyshev BPF structure [19-21]. The Chebyshev BPF has inferior selectivity due to the poor stopband rejection level. To improve selectivity in wide bandwidth, techniques of introducing transmission zeros to increase stopband by adding shunt capacitor, serial inductor, or shunt inductor have been presented [22-25]. The active BPF proposed in this research is shown in Figure 10. Two resonators are designed using active capacitor and active inductor in which the negative resistance of active capacitor compensates the resistive loss of active inductor as shown in Figure 11. The resistance compensation is optimized at the center frequency of 758 MHz. It achieves a gain of 18.1 dB, a Q factor of 107, and a stopband rejection of 50 dB. The BPF performance is shown in Figure 12. In Figure 10, [L.sub.DC] is added to produce the DC bias voltage and block the AC signal; [C.sub.AC] is added to bypass the AC signal and block the DC current. Figure 13 depicts capacitance versus frequency (before and after using [L.sub.DC] and [C.sub.AC]). Figure 14 depicts conductance versus frequency (before and after using [L.sub.DC] and [C.sub.AC]). As shown in Figures 13 and 14, after adding [L.sub.DC] and [C.sub.AC], the capacitance and negative conductance values are stable and almost constant in the frequency range [758 MHz, 864 MHz]. In Figure 10, after applying a DC supply voltage [V.sub.LD] and a resistor [R.sub.AD], a DC bias voltage (0.9 V) is obtained at [V.sub.X]. Figure 15 depicts inductance versus frequency (before and after using [R.sub.AD]) and Figure 16 shows resistance versus frequency (before and after using [R.sub.AD]).

As shown in Figures 15 and 16, after adding [R.sub.AD], the inductance and its positive resistance are slightly changed. The reason is explained below. From the analysis of the small signal equivalent model in Figure 11, [mathematical expression not reproducible] constitute a RLC parallel circuit.

In Figure 11(b), the admittance of this RLC parallel circuit equals

[mathematical expression not reproducible]. (17)

If [L.sub.DC] is large enough, 1/[omega][L.sub.DC] can be neglected. In Figure 11(c), if [C.sub.AC] is large enough, then

[mathematical expression not reproducible]. (18)

It means the effect of [C.sub.AC] can be neglected. On the other hand, [L.sub.DC] and [C.sub.AC] do not take part in the performance of BPF.

By adjusting [R.sub.AD], the input DC voltage of the active inductor can be adjusted to a desirable bias value accordingly. [R.sub.AD] is in parallel with [mathematical expression not reproducible], as shown in Figure 11(c).

In order to find a match between the negative resistance and the positive resistance, [mathematical expression not reproducible] is changed to [R.sub.p] in parallel with [L.sub.equ] where Q is quality factor of the active inductor.

[mathematical expression not reproducible], (19)

[mathematical expression not reproducible], (20)

[mathematical expression not reproducible], (21)

[mathematical expression not reproducible]. (22)

4.2. Performance Evaluation. The active inductor in this application provides a relative fixed value of inductance and resistance. By adjusting the bias voltage [V.sub.G], a tunable capacitance of the active capacitor is obtained, which makes this BPF tunable. Figure 17 displays the BPF tunability for the center frequency [758 MHz, 864 MHz], the 3dB bandwidth [7.1 MHz, 65.9 MHz], the gain [6.5 dB, 18.1 dB], the stopband rejection [38 dB, 50 dB], and the quality factor [12,107].

It is observed from Figure 17 that when [V.sub.G] is decreased (from the lower bound to the upper bound), the gain is decreased, and the 3 dB bandwidth is increased. At the center frequency of 758 MHz (red plot), the resistance loss of the active inductor is nearly cancelled by the negative resistance of the active capacitor, leading to an ideal resonator in the circuit.

Table 1 presents detailed analysis of six BPF center frequency cases (758 MHz, 770 MHz, 778 MHz, 800 MHz, 844 MHz, and 864 MHz) in Figure 17. In the active inductor column, [mathematical expression not reproducible] are the BPF design values; [L.sub.equ] and [R.sub.p] are the analysis values calculated from (19) and (20). In the active capacitor column, [mathematical expression not reproducible] are the BPF design values. Applying the [L.sub.equ] and [C.sub.equ] values, the theoretical center frequency [f.sub.0] is then calculated from (21). The BPF column presents quality factor, pass band gain, and bandwidth. By comparing the theoretical [f.sub.0] and the measured [f.sub.0] the error percentage [DELTA][f.sub.0] is about 1%. By comparing the analysis value [R.sub.p] and the design value [mathematical expression not reproducible] the error percentage [DELTA]R is less than 5%, which shows that the resistive loss of active inductor is almost cancelled by negative resistance of active capacitor.

Table 2 summarizes this and past work of classic Chebyshev bandpass filter. As shown in this table, the pass band gain, stopband rejection, and quality factor of the tunable BPF are much higher than those of most of the other works.

5. Conclusion

In this paper, a classic Chebyshev BPF adopting active capacitor and active inductor for tunability, low cost, and smaller size is presented. The tunability of BPF center frequency and pass band is achieved by controlling the active capacitance, which is tunable by adjusting the DC bias voltage. The negative resistance of active capacitor compensates 95% above the resistive loss of active inductor in the tunable center frequency range. A pass band gain of 18.1 dB and stopband rejection of 50 dB are obtained at the center frequency 758 MHz. The BPF achieves a high quality factor Q of 12-107 and a high stopband rejection of 38-50 dB.

https://doi.org/10.1155/2017/5369167

Conflicts of Interest

The authors declare that there are no conflicts of interest regarding the publication of this paper.

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Yu Wang, Jian Chen, and Chien-In Henry Chen

Department of Electrical Engineering, Wright State University, Dayton, OH 45435, USA

Correspondence should be addressed to Chien-In Henry Chen; henry.chen@wright.edu

Received 13 March 2017; Accepted 24 April 2017; Published 18 May 2017

Academic Editor: Chang-Ho Lee

Caption: Figure 1: The active capacitor and its equivalent circuit.

Caption: Figure 2: The small signal modal of active capacitor.

Caption: Figure 3: Tunable AC capacitance.

Caption: Figure 4: Tunable AC negative resistance.

Caption: Figure 5: Lossy single-ended gyrator-C active inductor.

Caption: Figure 6: The active inductor.

Caption: Figure 7: The small signal modal of active inductor.

Caption: Figure 8: Inductance of tunable AI.

Caption: Figure 9: Resistance of tunable AI.

Caption: Figure 10: The proposed tunable BPF.

Caption: Figure 11: Equivalent circuits of the resonator.

Caption: Figure 12: BPF performance.

Caption: Figure 13: Capacitance versus frequency (before and after using [L.sub.DC] and [C.sub.AC]).

Caption: Figure 14: Conductance versus frequency (before and after using [L.sub.DC] and [C.sub.AC]).

Caption: Figure 15: Inductance versus frequency (before and after using [R.sub.AD]).

Caption: Figure 16: Resistance versus frequency (before and after using [R.sub.AD]).

Caption: Figure 17: Tunable BPF gain versus signal freq.

Table 1: Tunable BPF performance. 6 Tunable BPF cases Active inductor [mathematical expression not reproducible] Case 1 ([f.sub.0] = 758.58 MHz) 15.78 Case 2 ([f.sub.0] = 770.31MHz) 15.79 Case 3 ([f.sub.0] = 778.48 MHz) 15.8 Case 4 ([f.sub.0] = 800.45 MHz) 15.81 Case 5 ([f.sub.0] = 844.63 MHz) 15.85 Case 6 ([f.sub.0] = 864.30 MHz) 15.86 6 Tunable BPF cases Active inductor [mathematical expression not reproducible] Case 1 ([f.sub.0] = 758.58 MHz) 121.64 Case 2 ([f.sub.0] = 770.31MHz) 121.94 Case 3 ([f.sub.0] = 778.48 MHz) 122.15 Case 4 ([f.sub.0] = 800.45 MHz) 122.74 Case 5 ([f.sub.0] = 844.63 MHz) 123.97 Case 6 ([f.sub.0] = 864.30 MHz) 124.54 6 Tunable BPF cases Active inductor [Q.sub.AI] Case 1 ([f.sub.0] = 758.58 MHz) 0.618 Case 2 ([f.sub.0] = 770.31MHz) 0.627 Case 3 ([f.sub.0] = 778.48 MHz) 0.633 Case 4 ([f.sub.0] = 800.45 MHz) 0.648 Case 5 ([f.sub.0] = 844.63 MHz) 0.678 Case 6 ([f.sub.0] = 864.30 MHz) 0.692 6 Tunable BPF cases Active inductor [L.sub.equ] (nH) Case 1 ([f.sub.0] = 758.58 MHz) 57.05 Case 2 ([f.sub.0] = 770.31MHz) 55.98 Case 3 ([f.sub.0] = 778.48 MHz) 55.28 Case 4 ([f.sub.0] = 800.45 MHz) 53.48 Case 5 ([f.sub.0] = 844.63 MHz) 50.28 Case 6 ([f.sub.0] = 864.30 MHz) 49.02 6 Tunable BPF cases Active inductor [R.sub.p] (OMEGA) Case 1 ([f.sub.0] = 758.58 MHz) 168.17 Case 2 ([f.sub.0] = 770.31MHz) 169.85 Case 3 ([f.sub.0] = 778.48 MHz) 171.03 Case 4 ([f.sub.0] = 800.45 MHz) 174.27 Case 5 ([f.sub.0] = 844.63 MHz) 181.01 Case 6 ([f.sub.0] = 864.30 MHz) 184.10 6 Tunable BPF cases Active capacitor [mathematical [C.sub.equ] expression not (fF) reproducible] Case 1 ([f.sub.0] = 758.58 MHz) -164.72 189.10 Case 2 ([f.sub.0] = 770.31MHz) -166.67 186.54 Case 3 ([f.sub.0] = 778.48 MHz) -168.30 184.35 Case 4 ([f.sub.0] = 800.45 MHz) -170.42 182.11 Case 5 ([f.sub.0] = 844.63 MHz) -173.11 178.71 Case 6 ([f.sub.0] = 864.30 MHz) -176.32 175.83 6 Tunable BPF cases Theoretical Practical [f.sub.0] [DELTA] (MHz) [f.sub.0] (% error) Case 1 ([f.sub.0] = 758.58 MHz) 766.13 758.58 Case 2 ([f.sub.0] = 770.31MHz) 778.71 770.31 Case 3 ([f.sub.0] = 778.48 MHz) 788.31 778.48 Case 4 ([f.sub.0] = 800.45 MHz) 806.40 800.45 Case 5 ([f.sub.0] = 844.63 MHz) 839.47 844.63 Case 6 ([f.sub.0] = 864.30 MHz) 857.57 864.30 6 Tunable BPF cases [DELTA] [f.sub.0](MHz) [DELTA]R (% error) Case 1 ([f.sub.0] = 758.58 MHz) 7.56 (0.99%) Case 2 ([f.sub.0] = 770.31MHz) 8.40 (1.1%) Case 3 ([f.sub.0] = 778.48 MHz) 9.82 (1.2%) Case 4 ([f.sub.0] = 800.45 MHz) 5.95 (0.74%) Case 5 ([f.sub.0] = 844.63 MHz) 5.16 (0.61%) Case 6 ([f.sub.0] = 864.30 MHz) 6.74 (0.79%) 6 Tunable BPF cases [DELTA]R, ([OMEGA]) [DELTA]R, (% error) Case 1 ([f.sub.0] = 758.58 MHz) 3.45 (2.1%) Case 2 ([f.sub.0] = 770.31MHz) 3.17 (1.9%) Case 3 ([f.sub.0] = 778.48 MHz) 2.74 (1.6%) Case 4 ([f.sub.0] = 800.45 MHz) 3.85 (2.2%) Case 5 ([f.sub.0] = 844.63 MHz) 7.90 (4.4%) Case 6 ([f.sub.0] = 864.30 MHz) 7.78 (4.2%) 6 Tunable BPF cases BPF [Q.sub.BPF] Gain (dB) Case 1 ([f.sub.0] = 758.58 MHz) 107 18.1 Case 2 ([f.sub.0] = 770.31MHz) 39 11.31 Case 3 ([f.sub.0] = 778.48 MHz) 22 8.54 Case 4 ([f.sub.0] = 800.45 MHz) 12 6.55 Case 5 ([f.sub.0] = 844.63 MHz) 14 7.59 Case 6 ([f.sub.0] = 864.30 MHz) 41 13.24 6 Tunable BPF cases BPF BW (MHz) Case 1 ([f.sub.0] = 758.58 MHz) 7.1 Case 2 ([f.sub.0] = 770.31MHz) 19.98 Case 3 ([f.sub.0] = 778.48 MHz) 34.83 Case 4 ([f.sub.0] = 800.45 MHz) 65.34 Case 5 ([f.sub.0] = 844.63 MHz) 59.37 Case 6 ([f.sub.0] = 864.30 MHz) 21.24 Table 2: The previously reported several works by using the same structure of classic Chebyshev bandpass filter. [1] [2] Technology process CMOS 0.18 [micro]m CMOS 0.18 [micro]m Active component Active capacitor -- Order 2 2 Center frequency (MHz) 5300 23500 BW (MHz) 1700 4000 Pass band gain (dB) 0.77 1.65 Stopband rejection (dB) 36.8 15.2 Power (mW) 2.2 4.2 Quality factor 3 6 Tunability Center freq. (MHz) -- -- Gain (dB) -- -- BW (MHz) -- -- Quality factor -- -- [5] [6] Technology process BJT BFP420 BJT BFR92A Active component Active inductor Active inductor Order 3 2 Center frequency (MHz) 1950 2100 BW (MHz) 10 15 Pass band gain (dB) -8 0 Stopband rejection (dB) -- -- Power (mW) 4 -- Quality factor 195 140 Tunability Center freq. (MHz) 1800-2050 -- Gain (dB) -8 -- BW (MHz) 10 -- Quality factor 180-205 -- [7] [8] Technology process BJT BFR92A CMOS 0.18 [micro]m Active component Active inductor -- Order 1 3 Center frequency (MHz) 600 2368 BW (MHz) 300 60 Pass band gain (dB) 0.1 1.8 Stopband rejection (dB) -- 30 Power (mW) 120 8.8 Quality factor 2 40 Tunability Center freq. (MHz) -- -- Gain (dB) -- -- BW (MHz) -- -- Quality factor -- -- This work Technology process CMOS 0.18 [micro]m Active component Active capacitor/inductor Order 2 Center frequency (MHz) 758 BW (MHz) 7.1 Pass band gain (dB) 18.1 Stopband rejection (dB) 50 Power (mW) 25.5 Quality factor 107 Tunability Center freq. (MHz) 758~864 Gain (dB) 6.5~18.1 BW (MHz) 7.1~65.9 Quality factor 12~107

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Title Annotation: | Research Article |
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Author: | Wang, Yu; Chen, Jian; Chen, Chien-In Henry |

Publication: | VLSI Design |

Date: | Jan 1, 2017 |

Words: | 4741 |

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